CN114268329A - Dual-frequency high-linearity demodulator - Google Patents
Dual-frequency high-linearity demodulator Download PDFInfo
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- CN114268329A CN114268329A CN202111523522.6A CN202111523522A CN114268329A CN 114268329 A CN114268329 A CN 114268329A CN 202111523522 A CN202111523522 A CN 202111523522A CN 114268329 A CN114268329 A CN 114268329A
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Abstract
The invention discloses a double-frequency high-linearity demodulator which comprises two frequency mixing cores, a local oscillator quadrature generation network and an intermediate frequency 90-degree mixing network; the two frequency mixing cores are respectively used for mixing the received half radio frequency input signal with a local oscillator orthogonal signal input by the local oscillator orthogonal generation network to form two paths of intermediate frequency signals and outputting the two paths of intermediate frequency signals to the same 90-degree mixing network; the local oscillator orthogonal generation network is connected with the two frequency mixing cores and used for converting a local oscillator single-ended input signal into four local oscillator orthogonal signals and then inputting the orthogonal signals into the frequency mixing cores; and the 90-degree mixing network is connected with the two mixing cores and is used for synthesizing and outputting the two paths of demodulated intermediate-frequency signals. The multi-standard receiver has scientific structural design, can simultaneously work in two working frequency bands of 24-30 GHz and 36-42 GHz, has better linearity and image rejection degree in the whole frequency band, and meets the use requirements of the multi-standard receiver.
Description
Technical Field
The invention relates to the technical field of integrated circuits, in particular to a dual-frequency high-linearity demodulator.
Background
In recent years, the application of the millimeter wave band to 5G communication has gradually become a hot spot. Compared with the current Sub-6G system, the communication is carried out in the millimeter wave frequency band, so that larger bandwidth and larger communication speed can be realized, various communication applications can be supported, and for communication, the requirement on the size of an antenna can be effectively reduced by high-frequency communication, and the miniaturization of equipment is easier to realize.
In order to better receive a high-frequency signal, it is necessary to perform frequency conversion using a mixer, and in particular, in a frequency conversion receiver, it is necessary to transmit a signal by shifting a high-frequency signal to a low frequency using a demodulator.
In a traditional receiver, a Hartley receiver architecture and a Weffer receiver architecture are widely applied to an image rejection system, so that image signals can be effectively rejected, and efficient transmission of the signals is realized. However, with the increase of the operating frequency, the discrete components and module circuits used in the conventional architecture have been difficult to meet the use requirements, and with the current requirement of miniaturization and integration, it is very important for the 5G millimeter wave communication application to design a fully integrated multi-mode wideband demodulator.
Disclosure of Invention
The invention aims to provide a dual-frequency high-linearity demodulator aiming at the technical defects in the prior art.
Therefore, the invention provides a dual-frequency high-linearity demodulator, which comprises two frequency mixing cores, a local oscillator quadrature generation network and an intermediate frequency 90-degree mixing network, wherein:
the two frequency mixing cores are respectively used for mixing the received half radio frequency input signal with a local oscillator orthogonal signal input by the local oscillator orthogonal generation network to form two paths of intermediate frequency signals and outputting the two paths of intermediate frequency signals to the same 90-degree mixing network;
the local oscillator quadrature generation network is connected with the two frequency mixing cores and is used for converting a local oscillator single-ended input signal into four local oscillator quadrature signals and then respectively outputting the two local oscillator quadrature signals to a frequency mixer in one frequency mixing core so as to mix the quadrature signals with a radio frequency input signal;
and the 90-degree mixing network is connected with the two mixing cores and is used for receiving four paths of intermediate frequency signals input by the two mixing cores, respectively combining the two paths of intermediate frequency signals of each mixing core to form two paths of combined intermediate frequency signals and outputting the two paths of combined intermediate frequency signals outwards.
Compared with the prior art, the double-frequency high-linearity demodulator provided by the invention has the advantages that the structure design is scientific, the demodulator can work in two working frequency bands of 24-30 GHz and 36-42 GHz simultaneously, the whole frequency band has good linearity and image suppression degree, the balance among power consumption, gain, isolation and design cost is good, the use requirement of a multi-standard receiver is met, and the double-frequency high-linearity demodulator has great practical significance.
Drawings
Fig. 1 is a block diagram of a dual-frequency high-linearity demodulator according to the present invention;
FIG. 2 is a schematic circuit diagram of a dual-frequency high linearity demodulator according to the present invention;
FIG. 3 is a diagram illustrating simulation results of conversion gain with variation of RF signal frequency in an embodiment of a dual-band high linearity demodulator according to the present invention;
FIG. 4 is a diagram illustrating simulation results of image rejection with changes in RF signal frequency for a dual-band high linearity demodulator according to an embodiment of the present invention;
FIG. 5 is a diagram illustrating simulation results of the dual-band high linearity demodulator according to the present invention, in an embodiment, IP1dB is shown along with the frequency variation of the RF signal;
fig. 6a is a diagram of a first spectrum simulation result at a fixed frequency point in a dual-frequency high linearity demodulator according to an embodiment of the present invention;
fig. 6b is a diagram of a spectrum simulation result at a fixed frequency point of a dual-frequency high linearity demodulator according to an embodiment of the present invention.
Detailed Description
The technical solutions of the present invention will be described clearly and completely with reference to the following embodiments of the present invention, and it should be understood that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
In the description of the present invention, it is to be understood that the terms "center", "longitudinal", "lateral", "up", "down", "front", "back", "left", "right", "vertical", "horizontal", "top", "bottom", "inner", "outer", and the like, indicate orientations or positional relationships based on those shown in the drawings, and are used only for convenience in describing the present invention and for simplicity in description, and do not indicate or imply that the referenced devices or elements must have a particular orientation, be constructed and operated in a particular orientation, and thus, are not to be construed as limiting the present invention. Furthermore, the terms "first", "second", etc. are used for descriptive purposes only and are not to be construed as indicating or implying relative importance or implicitly indicating the number of technical features indicated. Thus, a feature defined as "first," "second," etc. may explicitly or implicitly include one or more of that feature. In the description of the present invention, "a plurality" means two or more unless otherwise specified.
In the description of the present invention, it should be noted that, unless otherwise explicitly specified or limited, the terms "mounted," "connected," and "connected" are to be construed broadly, e.g., as meaning either a fixed connection, a removable connection, or an integral connection; can be mechanically or electrically connected; they may be connected directly or indirectly through intervening media, or they may be interconnected between two elements. The specific meaning of the above terms in the present invention can be understood by those of ordinary skill in the art through specific situations.
The present invention will be described in detail below with reference to the embodiments with reference to the attached drawings.
Referring to fig. 1 to 6b, the present invention provides a dual-frequency high linearity demodulator, which includes two mixing cores 100, an In-phase component/Quadrature component (I/Q) generating network 200, and an intermediate frequency 90 ° hybrid network 300, wherein:
the two frequency mixing cores 100 are respectively used for mixing the received half radio frequency input signal with a local oscillator orthogonal (I/Q) signal input by the local oscillator orthogonal generation network 200 to form two paths of intermediate frequency signals and outputting the two paths of intermediate frequency signals to the same 90-degree mixing network;
the local oscillator quadrature (I/Q) generation network 200 is connected to the two frequency mixing cores 100, and is configured to convert a local oscillator single-ended input signal into four local oscillator quadrature signals, and then output two paths of quadrature signals to a mixer 101 in one frequency mixing core 100, so that the quadrature signals are mixed with a radio frequency input signal;
it should be noted that the local oscillator single-ended input signal may be provided by an external signal source, and the external signal source is connected to a signal receiving end of the local oscillator quadrature (I/Q) generation network 200.
The 90 ° hybrid network is connected to the two mixing cores 100, and is configured to receive four intermediate frequency signals input by the two mixing cores 100 (two intermediate frequency signals are input by each mixing core 100), combine the two intermediate frequency signals of each mixing core 100 (specifically, perform in-phase signal superposition and image signal suppression processing), form two combined intermediate frequency signals, and output the two combined intermediate frequency signals to the outside, where the output intermediate frequency signals may be subjected to secondary mixing by an external device to a baseband for processing or directly accessed to the baseband for processing.
It should be noted that, for the present invention, a single-ended signal (i.e., a radio frequency input signal) input by a radio frequency is directly divided into two parts and respectively input to two frequency mixing cores, the local oscillator single-ended input signal is converted into four orthogonal signals through an I/Q generation network and is subjected to frequency mixing with the radio frequency input signal, upper and lower intermediate frequency signals output by the two frequency mixing cores 100 are synthesized through a 90 ° hybrid network, so that in-phase signal superposition and image signal suppression are realized, and finally, intermediate frequency signals demodulated by upper and lower sidebands of the radio frequency are respectively output through an "intermediate frequency output 1" port and an "intermediate frequency output 2" port.
In the present invention, in a specific implementation, each mixing core 100 includes a mixer 101, a single-slip transformer network 102 (i.e., a radio frequency balun in fig. 1) and an intermediate frequency balun (i.e., a Marchand balun) 103;
a single-slip transformer network 102, configured to convert one-half of the rf input signal into a differential rf input signal, and output the differential rf input signal to the mixer 101;
a mixer 101, configured to receive differential radio frequency input signals, perform mixing processing on the differential radio frequency input signals and local oscillator quadrature (I/Q) signals input by the local oscillator quadrature (I/Q) generation network 200 to form two differential intermediate frequency signals, and output the two differential intermediate frequency signals to the local oscillator quadrature (I/Q) generation network
The intermediate frequency balun (i.e., Marchand balun) 103 is configured to convert the two differential intermediate frequency signals into two single-ended intermediate frequency signals, and output the single-ended intermediate frequency signals to the 90 ° hybrid network.
In a specific implementation, the mixer 101 includes a radio frequency transconductance stage and a local oscillator switch stage;
the RF transconductance stage of the mixer 101 comprises a transistor M1～M4Capacitor C1～C4Inductor L1～L4；
Wherein, the inductance L1And L3Coupling to form a transformer;
inductor L2And L4Coupling into a transformer;
one ends of the capacitors C1 and C3 are connected with the differential radio frequency signal end RF +;
the other end of the capacitor C1 is connected with one end of the resistor R1 and the transistor M respectively3The grid electrodes are connected;
the other end of the capacitor C3 is connected with one end of the resistor R3 and the transistor M respectively1The grid electrodes are connected;
the other end of the resistor R1 is connected to an auxiliary voltage terminal Va for supplying power to the transconductance stage.
The other end of the resistor R3 is connected to a main voltage terminal Vm, which is used to power the transconductance stage.
Transistor M3And a transistor M1The drain electrodes of the two are connected;
transistor M1Source electrode of via inductor L1Grounding;
transistor M3The drain electrode of (1) is grounded;
transistor M1And a transistor M3After the bus bars cross, the source electrode of (1) passes through an inductor L3With transistor M in the local oscillator switching stage of mixer 1015And M6The source electrodes of the two are connected;
in a specific implementation, one end of each of the capacitors C2 and C4 is connected with a differential radio frequency signal end RF-;
the other end of the capacitor C2 is connected with one end of the resistor R2 and the transistor M respectively4The grid electrodes are connected;
the other end of the capacitor C4 is connected with one end of the resistor R4 and the transistor M respectively2The grid electrodes are connected;
the other end of the resistor R2 is connected to an auxiliary voltage terminal Va for supplying power to the transconductance stage.
The other end of the resistor R4 is connected to a main voltage terminal Vm, which is used to power the transconductance stage.
Transistor M4And a transistor M2The drain electrodes of the two are connected;
transistor M2Source electrode of via inductor L2Grounding;
transistor M4The drain electrode of (1) is grounded;
transistor M2And a transistor M4After the bus bars cross, the source electrode of (1) passes through an inductor L4With transistor M in the local oscillator switching stage of mixer 1017And M8The source electrodes of the two are connected;
in particular, the local oscillator switching stage of the mixer 101 comprises a transistor M5～M8And an inductance L5～L6；
Transistor M5And M6Respectively with the inductor L5And L6One ends of the two are connected;
inductor L5And L6The other end of the voltage regulator is connected with a total supply voltage VDD;
transistor M5The grid of the grid is connected with one path of local oscillation orthogonal signal LO + and is used for realizing the input of local oscillation signals;
transistor M7Of the drain electrodeRespectively associated with the inductor L5Connected to the intermediate frequency output IF +;
transistor M8Respectively with the inductor L6One end of the intermediate frequency output IF-is connected with the intermediate frequency output IF-;
transistor M7Gate of (D) and transistor M6The grid of the grid is connected with the local oscillator quadrature signal LO-at the same time;
transistor M8The grid of the grid is connected with one path of local oscillation orthogonal signal LO + and is used for realizing the input of local oscillation signals;
it should be noted that the rf input signal is converted into a differential signal through the single-slip transformer network 102, and then passes through the transistor M in the mixer 1011～M4The gate of (1) into; capacitor C1～C4The method is mainly used for isolating direct traffic; inductor L1～L4On the one hand for reducing the transistor M1～M4On the other hand, to improve the linearity of the transconductance stage. The incoming radio frequency signal RF (i.e. the differential radio frequency signal) passes through the transistor M1～M4The output of the drain electrode is a current signal, and the current signal enters a local oscillation switch stage of the frequency mixer 101 for frequency mixing;
it should be noted that the radio frequency signal RF (i.e. the differential radio frequency signal output by the radio frequency transconductance stage) passes through the switch tube M5～M8The source electrode of the local oscillator enters a local oscillator switch stage, and a local oscillator signal LO passes through a switch tube M5～M8The grid electrode enters a local oscillator switch stage, and the intermediate frequency signal after frequency mixing passes through a switch tube M5～M8To the intermediate frequency load inductor L5～L6；
It should be noted that, for the present invention, the frequency mixing core 100 is designed based on a gilbert cell, and the radio frequency transconductance stage of the frequency mixing core 100 is designed based on a multi-transistor parallel technology, and includes a main circuit and an auxiliary circuit, an input signal enters from a gate of a transistor, is converted into a current signal, is output from a drain, and further enters a local oscillation switch stage of the frequency mixing core 100 to perform frequency mixing, and through the structural design of the main circuit and the auxiliary circuit, the third-order intermodulation of the frequency mixer can be effectively improved. The source electrode of the main circuit transistor is connected with source electrode degenerationInductor L1And the drain electrode inductance L3A weak coupling transformer is formed, so that the input 1dB compression point of the mixer is effectively improved.
In the present invention, the single-slip transformer network 102 includes an inductor L7And an inductance L8Formed transformer and matching capacitor C5～C6And a matching inductance L9～L10；
Capacitor C5And an inductance L7And a single-ended radio frequency signal input terminal SinConnecting;
it should be noted that, where the network is a balun, the analysis of the balun is generally an integral for performing single-slip on the signal;
capacitor C5And an inductance L7The other ends of the two-way valve are all grounded;
capacitor C6And an inductance L8And a differential signal terminal Sout+Connecting;
capacitor C6And an inductance L8And the other end of (1) and a differential signal terminal Sout-Connecting;
differential signal terminal Sout+And a differential signal terminal SoutRespectively, to the differential radio frequency signal terminals RF + and RF-of the mixer 101.
It should be noted that the single-to-differential transformer network 102 is mainly used for converting an input single-ended signal (i.e., a single-ended rf signal) into a differential signal, the single-ended signal terminal of the single-to-differential transformer network 102 is connected to one terminal of the rf one-to-two input, and the differential signal terminal (S) is connected to the other terminal of the rf one-to-two inputout+Sout-) RF + and RF-of the mixer 101;
in the present invention, the if balun 103 includes four quarter-wavelength transmission lines;
differential input IFin+And IFin-Respectively connecting the quarter-wavelength transmission lines (first) and (second) to the ground;
single-ended output IFoutTwo sections of series-connected quarter-wave transmission lines (c) and (c) are coupled with each other, whereby the opposite transmission lines are coupled with each otherTo achieve conversion of the intermediate frequency differential signal to a single-ended signal.
It should be noted that the differential input IF of the intermediate frequency balun 103in+And IFin-Connected to the intermediate frequency outputs IF + and IF-of the mixer 101, a single-ended output IF of the intermediate frequency balun 103outIs connected to the inputs IF1 and IF2 of the 90 hybrid network 300.
It should be noted that, for the present invention, the intermediate frequency balun is designed by using Marchand balun, and can implement conversion from a differential signal with a lower intermediate frequency to a single-ended signal. The local oscillator I/Q (quadrature) generation network 200 is designed based on a transformer, and is configured to convert a differential signal into four quadrature signals. The 90-degree hybrid network 300 is based on a transmission line coupling design mechanism, and effectively reduces the length of a used line and amplitude-phase errors by increasing inductance.
In the present invention, in a specific implementation, the local oscillator quadrature (I/Q) generation network 200 is designed based on a transformer, and is a passive network structure, and can implement conversion from a single-ended local oscillator signal to four-way quadrature signals.
For local oscillator quadrature (I/Q) generation network 200, it includes an inductor L11～L14；
Inductor L11One end of the input signal is connected with the input signal IN +, and the other end of the input signal is connected with the output I +;
inductor L14One end is connected with an input signal IN-, and the other end is connected with an output I-;
inductor L12One end of the resistor is connected with the output signal Q-, and the other end of the resistor is connected with the resistor R5Is connected to the ground;
inductor L13One end of the resistor is connected with the output signal Q +, and the other end of the resistor is connected with the resistor R6 to the ground;
it should be noted that the input signals IN + and IN-are IN equal-amplitude and opposite-phase, the output signals I +, I-, Q + and Q-are IN equal-amplitude and phase difference of 90 degrees IN sequence, and the inductor L11And an inductance L12Are coupled with each other, inductance L13And an inductance L14Mutually coupled, thereby enabling generation of a differential input signal into a four-way quadrature single-ended signal;
it should be noted that the local oscillator input is a single-ended signal, so it is necessary to generate a differential local oscillator signal through the same network as the single-slip transformer network 102, and then generate four-way quadrature single-ended signals through the I/Q generation network, where the input of the local oscillator quadrature generation network 200 may be provided by an external signal source, and the output is connected to the LO + and LO-of the mixer 101.
In the present invention, in a specific implementation, the intermediate frequency 90 ° hybrid network 300 is designed based on a transmission line coupling principle, and is a four-port passive network, which can implement 90 ° phase shift of a target signal.
For a mid-frequency 90 ° hybrid network 300, it includes an inductance L15～L16；
Inductor L15One terminal, input signal IF1 and capacitor C7The other end of the output voltage is connected with an output OUT1 and a capacitor C8Connecting;
inductor L16One terminal, input signal IF2 and capacitor C8The other end of the output voltage is connected with an output OUT2 and a capacitor C7Connecting;
it should be noted that IF1 and IF2 output from the mixer core 100 implement sideband suppression, inductance L, through the 90 ° hybrid network 30015And an inductance L16Are coupled with each other to realize the change of the phase of the input signal, and a capacitor C7And C8To reduce the inductance value of the inductor, OUT1 and OUT2 output from the 90 ° quadrature generation network 300 correspond to the intermediate frequency output 1 and the intermediate frequency output 2, respectively.
In the invention, the whole topology is designed based on a Hartley architecture, and is improved on the basis, thereby realizing double-frequency work and image suppression.
In the invention, aiming at the broadband matching design, the local oscillator and the radio frequency port both adopt a multi-stage matching network based on a transformer, and the better matching and gain flattening are realized by adjusting the parameters of each element in the matching network.
In the invention, aiming at the dual-band work, the local oscillation working frequency band is selected between the radio frequency dual-band, and the upper and lower side bands are effectively utilized to realize the simultaneous demodulation of the upper and lower side bands.
In the invention, the specific implementation can be realized under the CMOS process, and the transistor is a field effect transistor.
In the present invention, as shown in fig. 3, it is a simulation result diagram of the conversion gain varying with the frequency of the radio frequency signal according to the embodiment of the present invention, wherein the signal with the intermediate frequency of 6GHz and the radio frequency of 24-30 GHz is demodulated and then output through the "intermediate frequency output 1" port in the 90 ° hybrid network 300, the signal with the radio frequency of 36-42 GHz is demodulated and then output through the "intermediate frequency output 2" port in the 90 ° hybrid network 300, the local oscillator frequency is 30-36 GHz, the lower sideband conversion gain is-9.0-7.7 dB, and the upper sideband conversion gain is-10.6-10.3 dB.
In the present invention, as shown in fig. 4, it is a simulation result diagram of the image rejection degree varying with the frequency of the radio frequency signal in the embodiment of the present invention, and the signal with the intermediate frequency of 6GHz and the radio frequency of 24-30 GHz is demodulated and then output through the "intermediate frequency output 1" port in the 90 ° hybrid network 300, and the signal with the radio frequency of 36-42 GHz is demodulated and then output through the "intermediate frequency output 2" port in the 90 ° hybrid network 300, and the local oscillation frequency is 30-36 GHz, and the image rejection ratio of the lower sideband is greater than 23dB, optimally can reach 31dB, and the image rejection ratio of the upper sideband is greater than 15dB, optimally can reach 18 dB.
In the present invention, as shown in fig. 5, the embodiment IP of the present invention is implemented1dBAccording to a simulation result graph of the frequency change of the radio frequency signals, the signals with the intermediate frequency of 6GHz and the radio frequency of 24-30 GHz are output through an intermediate frequency output 1 port in the 90-degree hybrid network 300 after being demodulated, the signals with the radio frequency of 36-42 GHz are output through an intermediate frequency output 2 port in the 90-degree hybrid network 300 after being demodulated, the local oscillation frequency is 30-36 GHz, the linearity in the band is integrally larger than 6.3dBm, and the optimal linearity can reach 9 dBm.
In the present invention, in a specific implementation, as shown in fig. 6, the graph is a frequency spectrum simulation result diagram under a fixed frequency point in the embodiment of the present invention, where the intermediate frequency of fig. 6a is 6GHz, the local oscillation frequency is 33GHz, the radio frequency is 27GHz, and the radio frequency input power is 0 dBm; the intermediate frequency of fig. 6b is 6GHz, the local oscillator frequency is 33GHz, the radio frequency is 39GHz, and the radio frequency input signal is 0 dBm.
Compared with the prior art, the dual-frequency high-linearity demodulator provided by the invention has the following beneficial effects:
1. the dual-frequency high-linearity demodulator provided by the invention can realize the demodulation of signals in dual frequency bands by adopting a method of combining an active frequency mixing core and a passive broadband network.
2. The dual-frequency high-linearity demodulator provided by the invention integrally adopts an image rejection framework, and can realize a better image rejection effect in a dual-frequency band.
3. The double-frequency high-linearity demodulator provided by the invention can realize good linearity in double frequency bands by adopting the transconductance stage based on the source-drain weak coupling transformer.
In summary, compared with the prior art, the dual-frequency high-linearity demodulator provided by the invention has a scientific structural design, can simultaneously work in two working frequency bands of 24-30 GHz and 36-42 GHz, has good linearity and image rejection degree in the whole frequency band, has good balance among power consumption, gain, isolation and design cost, meets the use requirements of a multi-standard receiver, and has great practical significance.
The foregoing is only a preferred embodiment of the present invention, and it should be noted that, for those skilled in the art, various modifications and decorations can be made without departing from the principle of the present invention, and these modifications and decorations should also be regarded as the protection scope of the present invention.
Claims (9)
1. A dual-frequency high linearity demodulator comprising two mixing cores (100), a local oscillator quadrature generation network (200) and an intermediate frequency 90 ° hybrid network (300), wherein:
the two frequency mixing cores (100) are respectively used for mixing one half of received radio frequency input signals with local oscillator orthogonal signals input by the local oscillator orthogonal generation network (200) to form two paths of intermediate frequency signals and outputting the two paths of intermediate frequency signals to the same 90-degree mixing network;
the local oscillator quadrature generation network (200) is connected with the two frequency mixing cores (100) and is used for converting a local oscillator single-ended input signal into four local oscillator quadrature signals and then respectively outputting the two local oscillator quadrature signals to a frequency mixer (101) in one frequency mixing core (100), so that the quadrature signals and a radio frequency input signal are subjected to frequency mixing;
and the 90-degree mixing network is connected with the two mixing cores (100) and is used for receiving four paths of intermediate frequency signals input by the two mixing cores (100), respectively combining the two paths of intermediate frequency signals of each mixing core (100) to form two paths of combined intermediate frequency signals and outputting the two paths of combined intermediate frequency signals outwards.
2. The dual-frequency high linearity demodulator according to claim 1, characterized in that each mixing core (100) comprises a mixer (101), a single slip transformer network (102) and an intermediate frequency balun (103);
the single-slip transformer network (102) is used for converting half of the radio frequency input signals into differential radio frequency input signals and then outputting the differential radio frequency input signals to the mixer (101);
a mixer (101) for receiving differential radio frequency input signal, mixing with local oscillator orthogonal signal input by the local oscillator orthogonal generation network (200) to form two differential intermediate frequency signals and outputting to
And the intermediate frequency balun (103) is used for converting the two paths of differential intermediate frequency signals into two paths of single-ended intermediate frequency signals and outputting the two paths of single-ended intermediate frequency signals to the 90-degree hybrid network.
3. The dual-frequency high linearity demodulator according to claim 2, characterized by a mixer (101) comprising a radio frequency transconductance stage and a local oscillator switching stage;
RF transconductance stage of a mixer (101) comprising a transistor M1～M4Capacitor C1～C4Inductor L1～L4；
Wherein, the inductance L1And L3Coupling to form a transformer;
inductor L2And L4Coupling into a transformer;
one ends of the capacitors C1 and C3 are connected with the differential radio frequency signal end RF +;
the other end of the capacitor C1 is connected with one end of the resistor R1 and the transistor M respectively3The grid electrodes are connected;
the other end of the capacitor C3 is connected with one end of the resistor R3 and the transistor M respectively1The grid electrodes are connected;
the other end of the resistor R1 is connected with an auxiliary voltage end Va;
the other end of the resistor R3 is connected with a main voltage terminal Vm;
transistor M3And a transistor M1The drain electrodes of the two are connected;
transistor M1Source electrode of via inductor L1Grounding;
transistor M3The drain electrode of (1) is grounded;
transistor M1And a transistor M3After the bus bars cross, the source electrode of (1) passes through an inductor L3And a transistor M in a local oscillator switching stage of the mixer (101)5And M6The source electrodes of the two are connected;
one ends of the capacitors C2 and C4 are connected with the differential radio frequency signal end RF-;
the other end of the capacitor C2 is connected with one end of the resistor R2 and the transistor M respectively4The grid electrodes are connected;
the other end of the capacitor C4 is connected with one end of the resistor R4 and the transistor M respectively2The grid electrodes are connected;
the other end of the resistor R2 is connected with an auxiliary voltage end Va;
the other end of the resistor R4 is connected with a main voltage terminal Vm;
transistor M4And a transistor M2The drain electrodes of the two are connected;
transistor M2Source electrode of via inductor L2Grounding;
transistor M4The drain electrode of (1) is grounded;
transistor M2And a transistor M4After the bus bars cross, the source electrode of (1) passes through an inductor L4And a transistor M in a local oscillator switching stage of the mixer (101)7And M8The sources of the two are connected.
4. A dual-frequency high linearity demodulator according to claim 3, characterized by a local oscillator switching stage of the mixer (101)Comprising a transistor M5～M8And an inductance L5～L6；
Transistor M5And M6Respectively with the inductor L5And L6One ends of the two are connected;
inductor L5And L6The other end of the voltage regulator is connected with a total supply voltage VDD;
transistor M5The grid of the grid is connected with one path of local oscillator quadrature signal LO +;
transistor M7Respectively with the inductor L5Connected to the intermediate frequency output IF +;
transistor M8Respectively with the inductor L6One end of the intermediate frequency output IF-is connected with the intermediate frequency output IF-;
transistor M7Gate of (D) and transistor M6The grid of the grid is connected with the local oscillator quadrature signal LO-at the same time;
transistor M8And the grid of the grid is connected with one path of local oscillator quadrature signal LO +.
5. The dual-band high linearity demodulator of claim 2 wherein the slip transformer network (102) comprises an inductor L7And an inductance L8Formed transformer and matching capacitor C5～C6And a matching inductance L9～L10；
Capacitor C5And an inductance L7And a single-ended radio frequency signal input terminal SinConnecting;
capacitor C5And an inductance L7The other ends of the two-way valve are all grounded;
capacitor C6And an inductance L8And a differential signal terminal Sout+Connecting;
capacitor C6And an inductance L8And the other end of (1) and a differential signal terminal Sout-Connecting;
differential signal terminal Sout+And a differential signal terminal SoutConnected to the differential radio frequency signal terminals RF + and RF-, respectively, of the mixer (101).
6. The dual-frequency high linearity demodulator according to claim 2, characterized by an intermediate frequency balun (103) comprising four quarter-wavelength transmission lines;
differential input IFin+And IFin-Respectively connecting the quarter-wavelength transmission lines (first) and (second) to the ground;
single-ended output IFoutTwo sections of serial quarter-wave transmission lines are connected, and the opposite transmission lines are coupled.
7. Double-frequency high-linearity demodulator, in accordance with claim 6, characterized in that the differential inputs IF of the intermediate frequency balun (103)in+And IFin-Connected to the intermediate frequency outputs IF + and IF-of the mixer (101), the single-ended output IF of the intermediate frequency balun (103)outIs connected to the inputs IF1 and IF2 of the 90 hybrid network (300).
8. The dual-frequency high linearity demodulator according to claim 1, characterized in that it comprises an inductance L for the local oscillator quadrature generation network (200)11～L14；
Inductor L11One end of the input signal is connected with the input signal IN +, and the other end of the input signal is connected with the output I +;
inductor L14One end is connected with an input signal IN-, and the other end is connected with an output I-;
inductor L12One end of the resistor is connected with the output signal Q-, and the other end of the resistor is connected with the resistor R5Is connected to the ground;
inductor L13One end is connected to the output signal Q + and the other end is connected to ground through a resistor R6.
9. The dual-frequency high linearity demodulator according to any of claims 1 to 8, characterized in that it comprises, for an intermediate frequency 90 ° hybrid network (300), an inductance L15～L16；
Inductor L15One terminal, input signal IF1 and capacitor C7The other end of the output voltage is connected with an output OUT1 and a capacitor C8Connecting;
inductor L16One terminal, input signal IF2 and capacitor C8The other end of the output voltage is connected with an output OUT2 and a capacitor C7Are connected.
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